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1 lt1610 1.7mhz, single cell micropower dc/dc converter n uses tiny capacitors and inductor n internally compensated n low quiescent current: 30 m a n operates with v in as low as 1v n 3v at 30ma from a single cell n 5v at 200ma from 3.3v n high output voltage capability: up to 28v n low shutdown current: < 1 m a n automatic burst mode tm switching at light load n low v cesat switch: 300mv at 300ma n 8-lead msop and so packages the lt ? 1610 is a micropower fixed frequency dc/dc converter that operates from an input voltage as low as 1v. intended for small, low power applications, it switches at 1.7mhz, allowing the use of tiny capacitors and inductors. the device can generate 3v at 30ma from a single cell (1v) supply. an internal compensation network can be connected to the lt1610s v c pin, eliminating two exter- nal components. no-load quiescent current of the lt1610 is 30 m a, and the internal npn power switch handles a 300ma current with a voltage drop of 300mv. the lt1610 is available in 8-lead msop and so packages. burst mode is a trademark of linear technology corporation. figure 1. 1-cell to 3v step-up converter efficiency n pagers n cordless phones n battery backup n lcd bias n portable electronic equipment features descriptio u applicatio s u typical applicatio u , ltc and lt are registered trademarks of linear technology corporation. c2 22 m f c1 22 m f 1 cell l1 4.7 m h d1 v out 3v 30ma c1, c2: avx taja226m006r d1: motorola mbr0520 l1: murata lqh1c4r7 1610 f01 + + r1 1m r2 681k 65 2 7 4 1 8 3 v in sw pgnd fb shdn gnd comp lt1610 v c load current (ma) 0.1 efficiency (%) 85 80 75 70 65 60 55 50 1 10 100 1610 ta01 v out = 3v v in = 1.5v v in = 1v v in = 1.25v
2 lt1610 absolute m axi m u m ratings w ww u package/order i n for m atio n w u u t jmax = 125 c, q ja = 160 c/w t jmax = 125 c, q ja = 120 c/w (note 1) v in voltage ................................................................ 8v sw voltage ............................................... C 0.4v to 30v fb voltage ..................................................... v in + 0.3v v c voltage ................................................................ 2v comp voltage .......................................................... 2v current into fb pin .............................................. 1ma shdn voltage ............................................................ 8v consult factory for military grade parts. maximum junction temperature ......................... 125 c operating temperature range (note 1) commercial ............................................. 0 c to 70 c extended commercial (note 2) .......... C 40 c to 85 c industrial ........................................... C 40 c to 85 c storage temperature range ................. C 65 c to 150 c lead temperature (soldering, 10 sec).................. 300 c order part number lt1610cs8 lt1610is8 s8 part marking 1610 1610i order part number lt1610cms8 ms8 part marking ltdt 1 2 3 4 v c fb shdn pgnd 8 7 6 5 comp gnd v in sw top view ms8 package 8-lead plastic msop 1 2 3 4 8 7 6 5 top view v c fb shdn pgnd comp gnd v in sw s8 package 8-lead plastic so parameter conditions min typ max units minimum operating voltage 0.9 1 v maximum operating voltage 8v feedback voltage l 1.20 1.23 1.26 v quiescent current v shdn = 1.5v, not switching 30 60 m a quiescent current in shutdown v shdn = 0v, v in = 2v 0.01 0.5 m a v shdn = 0v, v in = 5v 0.01 1.0 m a fb pin bias current l 27 80 na reference line regulation 1v v in 2v (25 c, 0 c) 0.6 1 %/v 1v v in 2v (70 c) 2 %/v 2v v in 8v (25 c, 0 c) 0.03 0.15 %/v 2v v in 8v (70 c) 0.2 %/v error amp transconductance d i = 2 m a25 m mhos error amp voltage gain 100 v/v switching frequency l 1.4 1.7 2 mhz maximum duty cycle 77 80 95 % l 75 95 % e lectr ic al c c hara terist ics the l denotes specifications which apply over the specified temperature range, otherwise specifications are at t a = 25 c. commercial grade 0 c to 70 c, v in = 1.5v, v shdn = v in , unless otherwise noted. (note 2)
3 lt1610 e lectr ic al c c hara terist ics the l denotes specifications which apply over the specified temperature range, otherwise specifications are at t a = 25 c. commercial grade 0 c to 70 c, v in = 1.5v, v shdn = v in , unless otherwise noted. (note 2) parameter conditions min typ max units switch current limit (note 3) 450 600 900 ma switch v cesat i sw = 300ma 300 350 mv l 400 mv switch leakage current v sw = 5v 0.01 1 m a shdn input voltage high 1v shdn input voltage low 0.3 v shdn pin bias current v shdn = 3v 10 m a v shdn = 0v 0.01 0.1 m a the l denotes specifications which apply over the specified temperature range, otherwise specifications are at t a = 25 c. industrial grade C 40 c to 85 c, v in = 1.5v, v shdn = v in , unless otherwise noted. parameter conditions min typ max units minimum operating voltage t a = 85 c 0.9 1 v t a = C 40 c 1.25 v maximum operating voltage 8v feedback voltage l 1.20 1.23 1.26 v quiescent current 30 60 m a quiescent current in shutdown v shdn = 0v, v in = 2v 0.01 0.5 m a v shdn = 0v, v in = 5v 0.01 1.0 m a fb pin bias current l 27 80 na reference line regulation 2v v in 8v (C 40 c) 0.03 0.15 %/v 2v v in 8v (85 c) 0.2 %/v error amp transconductance d i = 2 m a25 m mhos error amp voltage gain 100 v/v switching frequency (note 4) l 1.4 1.7 2 mhz maximum duty cycle (note 4) 77 80 95 % l 75 95 % switch current limit 450 600 900 ma switch v cesat i sw = 300ma 300 350 mv l 400 mv switch leakage current v sw = 5v 0.01 1 m a shdn input voltage high 1v shdn input voltage low 0.3 v shdn pin bias current v shdn = 3v 10 m a v shdn = 0v 0.01 0.1 m a note 1: absolute maximum ratings are those values beyond which the life of a device may be impaired. note 2: the lt1610c is guaranteed to meet specified performance from 0 c to 70 c and is designed, characterized and expected to meet these extended temperature limits, but is not tested at C 40 c and 85 c. the lt1610i is guaranteed to meet the extended temperature limits. note 3: current limit guaranteed by design and/or correlation to static test. current limit is affected by duty cycle due to ramp generator. see block diagram. note 4: not 100% tested at 85 c.
4 lt1610 typical perfor a ce characteristics uw current limit vs duty cycle v cesat vs current switch current (ma) 0 100 v cesat (mv) 200 300 400 500 600 100 200 300 400 1610 g01 500 600 t a = 85 c t a = 40 c t a = 25 c current limit (dc = 30%) vs temperature temperature ( c) ?0 200 switch current limit (ma) 300 400 500 600 800 ?5 02550 1610 g02 75 100 700 oscillator frequency vs input voltage feedback voltage shdn pin current vs shdn pin voltage transient response, circuit of figure 1 shdn voltage (v) 0 shdn current ( a) 30 40 50 35 8 1610 g07 20 10 0 12 4 67 v out 50mv/div ac coupled i l1 100ma/div 31ma 1ma i load v in = 1.25v 500 m s/div v out = 3v 1610 ta08 duty cycle (%) 0 current limit (ma) 800 700 600 500 400 300 200 100 0 80 1610 g03 20 40 60 100 70 10 30 50 90 t a = 25 c input voltage (v) 0 0 switching frequency (mhz) 0.25 0.75 1.00 1.25 2.50 1.75 2 4 5 1610 g04 0.50 2.00 2.25 1.50 13 6 7 8 t a = 25 c temperature ( c) ?0 1.210 feedback voltage (v) 1.215 1.220 1.225 1.230 1.240 ?5 02550 1610 g05 75 100 1.235 quiescent current vs temperature temperature ( c) ?0 quiescent current ( a) 15 20 25 25 75 1610 g06 10 5 0 ?5 0 50 30 35 40 100 burst mode operation, circuit of figure 1 v out 20mv/div ac coupled switch voltage 2v/div v in = 1.25v 20 m s/div v out = 3v i load = 3ma 1610 ta08 switch current 50ma/div
5 lt1610 pi n fu n ctio n s uuu v c (pin 1): error amplifier output. frequency compensa- tion network must be connected to this pin, either internal (comp pin) or external series rc to ground. 220k w / 220pf typical value. fb (pin 2): feedback pin. reference voltage is 1.23v. connect resistive divider tap here. minimize trace area at fb. set v out according to v out = 1.23v (1 + r1/r2). shdn (pin 3): shutdown. ground this pin to turn off device. tie to 1v or more to enable. pgnd (pin 4): power ground. tie directly to local ground plane. sw (pin 5): switch pin. connect inductor/diode here. minimize trace area at this pin to keep emi down. v in (pin 6): input supply pin. must be locally bypassed. gnd (pin 7): signal ground. carries all device ground current except switch current. tie to local ground plane. comp (pin 8): internal compensation network. tie to v c pin, or let float if external compensation is used. output capacitor must be tantalum if comp pin is used for com- pensation. block diagra w fb fb bias v c r5 40k 1.7mhz oscillator ramp generator ff s rq 0.15 v in v in + + comp 4 7 3 8 5 6 1 + a = 3 v out sw gnd q1 q2 10 q3 pgnd a2 1610 f02 shdn shutdown enable comparator driver r6 40k r3 30k r2 (external) r c c c r4 140k r1 (external) + a1 g m 2 s figure 2. lt1610 block diagram
6 lt1610 applicatio n s i n for m atio n wu u u operation the lt1610 combines a current mode, fixed frequency pwm architecture with burst mode micropower operation to maintain high efficiency at light loads. operation can be best understood by referring to the block diagram in figure 2. q1 and q2 form a bandgap reference core whose loop is closed around the output of the converter. when v in is 1v, the feedback voltage of 1.23v, along with an 70mv drop across r5 and r6, forward biases q1 and q2s base collector junctions to 300mv. because this is not enough to saturate either transistor, fb can be at a higher voltage than v in . when there is no load, fb rises slightly above 1.23v, causing v c (the error amplifiers output) to decrease. when v c reaches the bias voltage on hysteretic comparator a1, a1s output goes low, turning off all circuitry except the input stage, error amplifier and low- battery detector. total current consumption in this state is 30 m a. as output loading causes the fb voltage to de- crease, a1s output goes high, enabling the rest of the ic. switch current is limited to approximately 100ma initially after a1s output goes high. if the load is light, the output voltage (and fb voltage) will increase until a1s output goes low, turning off the rest of the lt1610. low fre- quency ripple voltage appears at the output. the ripple frequency is dependent on load current and output capaci- tance. this burst mode operation keeps the output regu- lated and reduces average current into the ic, resulting in high efficiency even at load currents of 1ma or less. if the output load increases sufficiently, a1s output remains high, resulting in continuous operation. when the lt1610 is running continuously, peak switch current is controlled by v c to regulate the output voltage. the switch is turned on at the beginning of each switch cycle. when the sum- mation of a signal representing switch current and a ramp generator (introduced to avoid subharmonic oscillations at duty factors greater than 50%) exceeds the v c signal, comparator a2 changes state, resetting the flip-flop and turning off the switch. output voltage increases as switch current is increased. the output, attenuated by a resistor divider, appears at the fb pin, closing the overall loop. frequency compensation is provided by either an external series rc network connected between the v c pin and ground or the internal rc network on the comp pin (pin 8). the typical values for the internal rc are 50k and 50pf. layout although the lt1610 is a relatively low current device, its high switching speed mandates careful attention to layout for optimum performance. for boost converters, follow the component placement indicated in figure 3 for the best results. c2s negative terminal should be placed close to pin 4 of the lt1610. doing this reduces switching currents in the ground copper which keeps high frequency spike noise to a minimum. tie the local ground into the system ground plane at one point only, using a few vias, to avoid introducing di/dt induced noise into the ground plane. 1 2 8 7 3 4 6 5 l1 c2 lt1610 v out v in gnd shutdown r1 r2 multiple vias ground plane 1610 f03 + c1 d1 + figure 3. recommended component placement for boost converter. note direct high current paths using wide pc traces. minimize trace area at pin 1 (v c ) and pin 2 (fb). use multiple vias to tie pin 4 copper to ground plane. use vias at one location only to avoid introducing switching currents into the ground plane
7 lt1610 applicatio n s i n for m atio n wu u u a sepic (single-ended primary inductance converter) schematic is shown in figure 4. this converter topology produces a regulated output over an input voltage range 1 2 8 7 3 4 6 5 c2 lt1610 v in gnd shutdown r1 r2 multiple vias ground plane 1610 f05 + c3 d1 v out l1 l2 c1 + figure 5. recommended component placement for sepic shutdown c2 22 m f 6.3v c1 22 m f 6.3v l1 22 m h l2 22 m h c3 1 f ceramic d1 input li-ion 3v to 4.2v v out 3.3v 120ma 1610 f04 + + 1m 604k c1, c2: avx taja226m006 c3: avx 1206yc105 (x7r) d1: motorola mbr0520 l1, l2: murata lqh3c220 (uncoupled) or sumida cls62-220 (coupled) 65 2 3 4 7 8 1 v in sw pgnd fb shdn gnd comp lt1610 v c figure 4. li-ion to 3.3v sepic dc/dc converter that spans (i.e., can be higher or lower than) the output. recommended component placement for a sepic is shown in figure 5.
8 lt1610 applicatio n s i n for m atio n wu u u component selection inductors inductors used with the lt1610 should have a saturation current rating (C30% of zero current inductance) of ap- proximately 0.5a or greater. dcr should be 0.5 w or less. the value of the inductor should be matched to the power requirements and operating voltages of the application. in most cases a value of 4.7 m h or 10 m h is suitable. the murata lqh3c inductors specified throughout the data sheet are small and inexpensive, and are a good fit for the lt1610. alternatives are the cd43 series from sumida and the do1608 series from coilcraft. these inductors are slightly larger but will result in slightly higher circuit efficiency. chip inductors, although tempting to use because of their small size and low cost, generally do not have enough energy storage capacity or low enough dcr to be used successfully with the lt1610. diodes the motorola mbr0520 is a 0.5 amp, 20v schottky diode. this is a good choice for nearly any lt1610 application, unless the output voltage or the circuit topology require a diode rated for higher reverse voltages. motorola also offers the mbr0530 (30v) and mbr0540 (40v) versions. most one-half amp and one amp schottky diodes are suitable; these are available from many manufacturers. if you use a silicon diode, it must be an ultrafast recovery type. efficiency will be lower due to the silicon diodes higher forward voltage drop. capacitors the input capacitor must be placed physically close to the lt1610. esr is not critical for the input. in most cases inexpensive tantalum can be used. the choice of output capacitor is far more important. the quality of this capacitor is the greatest determinant of the output voltage ripple. the output capacitor performs two major functions. it must have enough capacitance to satisfy the load under transient conditions and it must shunt the ac component of the current coming through the diode from the inductor. the ripple on the output results when this ac current passes through the finite impedance of the output capacitor. the capacitor should have low impedance at the 1.7mhz switching frequency of the lt1610. at this frequency, the impedance is usually dominated by the capacitors equivalent series resistance (esr). choosing a capacitor with lower esr will result in lower output ripple. perhaps the best way to decrease ripple is to add a 1 m f ceramic capacitor in parallel with the bulk output capaci- tor. ceramic capacitors have very low esr and 1 m f is enough capacitance to result in low impedance at the switching frequency. the low impedance can have a dramatic effect on output ripple voltage. to illustrate, examine figure 6s circuit, a 4-cell to 5v/100ma sepic dc/dc converter. this design uses inexpensive aluminum electrolytic capacitors at input and output to keep cost down. figure 7 details converter operation at a 100ma load, without ceramic capacitor c5. note the 400mv spikes on v out . after c5 is installed, output ripple decreases by a factor of 8 to about 50mv p-p . the addition of c5 also improves efficiency by 1 to 2 percent. low esr and the required bulk output capacitance can be obtained using a single larger output capacitor. larger tantalum capacitors, newer capacitor technologies (for example the poscap from sanyo and spcap from panasonic) or large value ceramic capacitors will reduce the output ripple. note, however, that the stability of the circuit depends on both the value of the output capacitor and its esr. when using low value capacitors or capaci- tors with very low esr, circuit stability should be evalu- ated carefully, as described below. loop compensation the lt1610 is a current mode pwm switching regulator that achieves regulation with a linear control loop. the lt1610 provides the designer with two methods of com- pensating this loop. first, you can use an internal compen- sation network by tying the comp pin to the v c pin. this results in a very small solution and reduces the circuits total part count. the second option is to tie a resistor r c and a capacitor c c in series from the v c pin to ground. this allows optimization of the transient response for a wide variety of operating conditions and power components.
9 lt1610 applicatio n s i n for m atio n wu u u v out 200mv/div i diode 500ma/div switch voltage 10v/div 100ns/div 1610 f07 figure 7. switching waveforms without ceramic capacitor c5 v out 50mv/div i diode 500ma/div switch voltage 10v/div v in = 4.1v 100ns/div 1610 f08 load = 100ma figure 8. switching waveforms with ceramic capacitor c5. note the 50mv/div scale for v out figure 6. 4-cell alkaline to 5v/120ma sepic dc/dc converter it is best to choose the compensation components empiri- cally. once the power components have been chosen (based on size, efficiency, cost and space requirements), a working circuit is built using conservative (or merely guessed) values of r c and c c . then the response of the circuit is observed under a transient load, and the compen- sation network is modified to achieve stable operation. linear technologys application note 19 contains a de- tailed description of the method. a good starting point for the lt1610 is c c ~ 220pf and r c ~ 220k. all ceramic, low profile design large value ceramic capacitors that are suitable for use as the main output capacitor of an lt1610 regulator are now available. these capacitors have very low esr and there- fore offer very low output ripple in a small package. however, you should approach their use with some caution. ceramic capacitors are manufactured using a number of dielectrics, each with different behavior across tempera- ture and applied voltage. y5v is a common dielectric used for high value capacitors, but it can lose more than 80% of the original capacitance with applied voltage and extreme temperatures. the transient behavior and loop stability of the switching regulator depend on the value of the output capacitor, so you may not be able to afford this loss. other dielectrics (x7r and x5r) result in more stable character- istics and are suitable for use as the output capacitor. the x7r type has better stability across temperature, whereas the x5r is less expensive and is available in higher values. the second concern in using ceramic capacitors is that many switching regulators benefit from the esr of the shutdown c2 22 m f 6.3v c1 22 m f 6.3v l1 22 m h l2 22 m h c3 1 f ceramic d1 v out 5v 120ma 1610 f06 + + c4 1 m f ceramic 1m 324k c1, c2: aluminum electrolytic c3 to c5: ceramic x7r or x5r d1: mbr0520 l1, l2: murata lqh3c220 or sumida cls62-220 c5 1 m f ceramic 65 2 3 4 7 8 1 v in sw pgnd fb shdn gnd comp lt1610 v c 4 cells
10 lt1610 applicatio n s i n for m atio n wu u u output capacitor because it introduces a zero in the regulators loop gain. this zero may not be effective because the ceramic capacitors esr is very low. most current mode switching regulators (including the lt1610) can easily be compensated without this zero. any design should be tested for stability at the extremes of operating temperatures; this is particularly so of circuits that use ceramic output capacitors. figure 9 details a 2.5v to 5v boost converter. transient response to a 5ma to 105ma load step is pictured in figure 10. the double trace of v out at 105ma load is due to the esr of c2. this esr aids stability. in figure 11, c2 is replaced by a 10 m f ceramic capacitor. note the low phase margin; at higher input voltage, the converter may oscil- late. after replacing the internal compensation network with an external 220pf/220k series rc, the transient response is shown in figure 12. this is acceptable tran- sient response. table 1 figure c2 compensation 10 avx taja226m006 tantalum internal 11 taiyo yuden jmk316bj106 internal 12 taiyo yuden jmk316bj106 220pf/220k c2 22 m f r2 324k c1 22 m f l1 10 m h d1 v out 5v 100ma v in 2.5v 1610 f09 + + 1m r c c c c1: avx taja226m006 c2: see table d1: motorola mbr0520 l1: murata lqh30100 65 2 7 4 8 1 3 v in sw pgnd fb shdn gnd v c lt1610 comp figure 9. 2.5v to 5v boost converter can operate with a ceramic output capacitor as long as proper r c and c c are used. disconnect comp pin if external compensation components are used v out 100mv/div 105ma 5ma load current 500 m s/div 1610 f10 figure 10. tantalum output capacitor and internal rc compensation v out 100mv/div 105ma 5ma load current 500 m s/div 1610 f11 figure 11. 10 m f x5r-type ceramic output capacitor and internal rc compensation has low phase margin v out 100mv/div 105ma 5ma load current 500 m s/div 1610 f12 figure 12. ceramic output capacitor with 220pf/220k external compensation has adequate phase margin
11 lt1610 typical applicatio n s u c2 15 m f c1 15 m f 2 cells l1 4.7 m h d1 v out 5v 50ma 1610 ta02 + + 1m 324k c1, c2: avx taja156m010r d1: motorola mbr0520 l1: sumida cd43-4r7 murata lqh1c4r7 65 2 7 4 1 8 3 v in sw pgnd fb shdn gnd comp lt1610 v c load current (ma) 0.1 efficiency (%) 90 80 70 60 50 110 1610 ta03 100 1000 v in = 1.5v v in = 3v v in = 2v efficiency 2-cell to 5v converter c2 33 m f c1 10 m f 2 cells l1 4.7 m h d1 v out 3.3v 70ma 1610 ta04 + + r2 1m r3 604k c1: avx taja106m010r c2: avx tajb336m006r d1: mbr0520 l1: murata lqh3c4r7 65 2 3 4 7 8 1 v in sw pgnd fb v c shdn comp lt1610 shutdown gnd load (ma) 60 efficiency (%) 70 80 90 0.1 10 100 1000 1610 ta05 50 1 3.3v out 3v in 1.5v in 2v in efficiency 2-cell to 3.3v converter efficiency 5v to 12v/100ma boost converter load current (ma) 0.1 70 efficiency (%) 80 90 1 10 100 1610 ta07 60 65 75 85 55 50 c2 15 m f l1 10 m h v in 5v d1 v out 12v 100ma 1610 ta06 + c1 15 m f + r2 1m r3 115k c1: avx taja156m010 c2: avx tajb156m016 d1: motorola mbr0520 l1: murata lqh3c100m24 65 2 3 4 7 8 1 v in sw pgnd fb v c shdn comp lt1610 shutdown gnd
12 lt1610 typical applicatio n s u c2 15 m f l1 10 m h v in 5v d1 v out 9v 150ma 1610 ta08 + c1 15 m f + r2 1m r3 158k c1: avx taja156m010 c2: avx tajb156m016 d1: motorola mbr0520 l1: murata lqh3c100m24 65 2 3 4 7 8 1 v in sw pgnd fb v c shdn comp lt1610 shutdown gnd 5v to 9v/150ma boost converter efficiency load current (ma) 1 70 efficiency (%) 80 90 10 100 300 1610 ta09 60 65 75 85 55 50 v out 200mv/div 140ma 10ma load current inductor current 200ma/div 200 m s/div 1610 ta10 5v to 9v boost converter transient response
13 lt1610 typical applicatio n s u 3.3v to 8v/70ma, C 8v/5ma, 24v/5ma tft lcd bias supply uses all ceramic capacitors d1 d4 0.22 f l1 5.4 h 65 8 2 4 7 3 1 v in sw lt1610 pgnd comp v c fb shdn gnd 0.22 f 100k 48.7k 1610 ta18 274k c1 4.7 f v in 3.3v c2 4.7 f 1 f 1 f 1 f 0.22 f av dd 8v 70ma 0.22 f: taiyo yuden emk212bj224mg 1 f: taiyo yuden lmk212bj105mg 4.7 f: taiyo yuden lmk316bj475ml d1: motorola mbro520 d2, d3, d4: bat54s l1: sumida cdrh5d185r4 v on 24v 5ma v off ?v 5ma 51pf d3 d2 tft lcd bias supply transient response av dd 200mv/div v on 500mv/div v off 200mv/div 70ma 25ma av dd load 200 m s/div 1610 ta19 v on load = 5ma v off load = 5ma
14 lt1610 typical applicatio n s u c big c1 15 m f 15k 1 aa alkaline charge shutdown l1 4.7 m h d1 q1 v out 4.5v c1, c2: avx taja156m010 d1: motorola mbr0530t1 l1: murata lqh1c4r7 q1: 2n3906 1610 ta11 + c2 15 m f + + r1 200k r4 20 r3 845k r2 2m 65 8 2 4 3.3nf 7 1 3 v in sw pgnd comp shdn fb v c lt1610 gnd single cell super cap charger output voltage (v) 2.0 0 output current (ma) 5 10 15 20 25 2.5 3.0 3.5 4.0 1610 ta12 4.5 5.0 output voltage (v) 2.0 0 output power (mw) 10 20 30 40 60 2.5 3.0 3.5 4.0 1610 ta13 4.5 5.0 50 super cap charger output current vs output voltage super cap charger output power vs output voltage
15 lt1610 package descriptio n u dimensions in inches (millimeters) unless otherwise noted. s8 package 8-lead plastic small outline (narrow 0.150) (ltc dwg # 05-08-1610) ms8 package 8-lead plastic msop (ltc dwg # 05-08-1660) msop (ms8) 1197 * dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.006" (0.152mm) per side ** dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.006" (0.152mm) per side 0.021 0.006 (0.53 0.015) 0 ?6 typ seating plane 0.007 (0.18) 0.040 0.006 (1.02 0.15) 0.012 (0.30) ref 0.006 0.004 (0.15 0.102) 0.034 0.004 (0.86 0.102) 0.0256 (0.65) typ 12 3 4 0.192 0.004 (4.88 0.10) 8 7 6 5 0.118 0.004* (3.00 0.102) 0.118 0.004** (3.00 0.102) 1 2 3 4 0.150 ?0.157** (3.810 ?3.988) 8 7 6 5 0.189 ?0.197* (4.801 ?5.004) 0.228 ?0.244 (5.791 ?6.197) 0.016 ?0.050 (0.406 ?1.270) 0.010 ?0.020 (0.254 ?0.508) 45 0 ?8 typ 0.008 ?0.010 (0.203 ?0.254) so8 0996 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) typ dimension does not include mold flash. mold flash shall not exceed 0.006" (0.152mm) per side dimension does not include interlead flash. interlead flash shall not exceed 0.010" (0.254mm) per side * **
16 lt1610 1610f lt/tp 0699 4k ? printed in usa ? linear technology corporation 1998 typical applicatio n s n u li-ion to 3.3v sepic dc/dc converter part number description comments ltc ? 1474 micropower step-down dc/dc converter 94% efficiency, 10 m a i q , 9v to 5v at 250ma lt1307 single cell micropower 600khz pwm dc/dc converter 3.3v at 75ma from 1 cell, msop package ltc1440/1/2 ultralow power single/dual comparators with reference 2.8 m a i q , adjustable hysteresis ltc1502-3.3 single cell to 3.3v regulated charge pump 40 m a i q , no inductors, 3.3v at 10ma from 1v input lt1521 micropower low dropout linear regulator 500mv dropout, 300ma current, 12 m a i q lt1611 inverting 1.4mhz dc/dc converter 5v to C 5v at 150ma, tiny sot-23 package lt1613 step-up 1.4mhz dc/dc converter 3.3v to 5v at 200ma, tiny sot-23 package ltc1682 doubler charge pump with low noise linear regulator fixed 3.3v and 5v outputs, 1.8v to 4.4v input range, 50ma output related parts linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 l fax: (408) 434-0507 l www.linear-tech.com shutdown c2 22 m f 6.3v c1 22 m f 6.3v l1 22 m h l2 22 m h c3 1 f ceramic d1 input li-ion 3v to 4.2v v out 3.3v 120ma 1610 ta14 + + 1m 604k c1, c2: avx tajb226m006 c3: avx 1206yc105 (x7r) d1: motorola mbr0520 l1, l2: murata lqh3c220 (uncoupled) or sumida cls62-220 (coupled) 65 2 3 4 7 8 1 v in sw pgnd fb shdn gnd comp lt1610 v c efficiency load current (ma) 0.1 efficiency (%) 60 70 80 1 10 100 1610 ta15 50 40 30 v in = 2.7v v in = 3.6v v in = 4.2v shutdown c2 22 m f 6.3v c1 22 m f 6.3v l1 22 m h l2 22 m h c3 1 f ceramic d1 v out 5v 120ma 1610 ta16 + + 1m 324k c1, c2: avx tajb226m006 c3: avx 1206yc105 (x7r) d1: motorola mbr0520 l1, l2: murata lqh3c220 (uncoupled) or sumida cls62-220 (coupled) 65 2 3 4 7 8 1 v in sw pgnd fb shdn gnd comp lt1610 v c 4 cells 4-cell to 5v/120ma sepic dc/dc converter load current (ma) 0.1 efficiency (%) 60 70 80 1 10 100 1610 ta17 50 40 30 v in = 3.6v v in = 4.2v v in = 5v v in = 6.5v 4-cell to 5v efficiency

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